Magnetic integration double-ended converter

ABSTRACT

A magnetic integration double-ended converter with an integrated function of a transformer and an inductor includes an integrated magnetic member having a magnetic core with three magnetic columns having at least three windings (N P , N S1 , N S2 ) and at least one energy storage air gap, where a primary winding (N P ) and a first secondary winding (N S1 ) are both wound around a first magnetic column or are both wound around a second magnetic column and a third magnetic column, and a second secondary winding (N S2 ) is wound around the second magnetic column; an inverter circuit with double ends symmetrically working, acting on the primary winding (N P ); and a group of synchronous rectifiers (SR 1 , SR 2 ), gate electrode driving signals of which and gate electrode driving signals of a group of power switch diodes (S 1 , S 2 ) of the inverter circuit with the double ends symmetrically working complement each other.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of International Application No.PCT/CN2011/070353, filed on Jan. 18, 2011, which claims priority toChinese Patent Application No. 201010004094.1, filed on Jan. 19, 2010and Chinese Patent Application No. 201010266511.X, filed on Aug. 30,2010, all of which are hereby incorporated by reference in theirentireties.

FIELD OF THE APPLICATION

The present application relates to a magnetic integration double-endedconverter with an integrated function of a transformer and an inductor.

BACKGROUND OF THE APPLICATION

In an application scenario of direct-current converter with a wide-rangeinput voltage, according to requirements of a power level, asingle-ended converter (such as a flyback converter or a forwardconverter) or a double-ended converter (such as a half-bridge converter,a full-bridge converter, or a push-pull converter) may be used as a mainpower topology.

FIG. 1 shows an existing magnetic integration half-bridge converter,where an integrated magnetic member is an EE-type magnetic core, awinding N_(P) and a winding N_(S) are wound around a central column ofthe EE-type magnetic core to form a transformer, and a winding N_(L1)and a winding N_(L2) are wound around side columns of the EE-typemagnetic core to form an inductor.

During implementation application, the above prior art at least has theproblems of a significant loss of the windings and a large leakageinductance.

SUMMARY OF THE APPLICATION

Embodiments of the present application provide a magnetic integrationdouble-ended converter, capable of reducing a loss of the windings and aleakage inductance of a primary side and a secondary side, andimplementing high efficient conversion of energy.

An embodiment of the present application provides a magnetic integrationdouble-ended converter, which includes:

-   -   an inverter circuit with double ends symmetrically working,        acting on a primary winding;    -   an integrated magnetic member having a magnetic core with three        magnetic columns, including at least three windings and at least        one energy storage air gap, where the primary winding and a        first secondary winding are both wound around a first magnetic        column, a second secondary winding is wound around the second        magnetic column, and a total output current flows through the        second secondary winding; and    -   a group of synchronous rectifiers, gate electrode driving        signals of which and gate electrode driving signals of a group        of power switch diodes of the inverter circuit with the double        ends symmetrically working complement each other.

An embodiment of the present application provides another magneticintegration double-ended converter, which includes:

-   -   an inverter circuit with double ends symmetrically working,        acting on a primary winding;    -   an integrated magnetic member having a magnetic core with three        magnetic columns, including at least three windings and at least        one energy storage air gap, where the primary winding and a        first secondary winding are both wound around a second magnetic        column and a third magnetic column, a second secondary winding        is wound around the second magnetic column, and a total output        current flows through the second secondary winding; and    -   a group of synchronous rectifiers, gate electrode driving        signals of which and gate electrode driving signals of a group        of power switch diodes of the inverter circuit with the double        ends symmetrically working complement each other.

It can be known from the technical solutions provided the embodiments ofthe present application that, the primary winding and the firstsecondary winding are wound around the same magnetic column, and thesynchronous rectifier replaces a rectifier diode in the prior art,thereby reducing a turn-on loss of a switch device, and playing a partin zero voltage drop clamping of the secondary winding. In this way,least primary windings may be adopted to implement energy transferringfrom the primary side to the secondary side, thereby reducing a loss ofthe windings and a leakage inductance of the primary side and thesecondary side, and implementing high efficient conversion of energy.

BRIEF DESCRIPTION OF THE DRAWINGS

To illustrate the technical solutions according to the embodiments ofthe present application more clearly, the following briefly introducesthe accompanying drawings for describing the prior art and theembodiments of the present application.

FIG. 1 shows a magnetic integration half-bridge converter in the priorart;

FIG. 2 shows a magnetic integration half-bridge converter provided inEmbodiment 1 of the present application;

FIG. 3 is a schematic analysis diagram of an integrated magnetic memberhaving a magnetic integration double-ended converter provided inEmbodiment 1 of the present application;

FIG. 4 is a schematic diagram of a working waveform of the magneticintegration half-bridge converter provided in Embodiment 1 of thepresent application;

FIG. 5 shows a magnetic integration half-bridge converter provided inEmbodiment 2 of the present application;

FIG. 6 is a schematic diagram of a working waveform of the magneticintegration half-bridge converter provided in Embodiment 2 of thepresent application;

FIG. 7 shows a magnetic integration half-bridge converter provided inEmbodiment 3 of the present application;

FIG. 8 shows a magnetic integration full-bridge inverter provided in anembodiment of the present application;

FIG. 9 shows a magnetic integration push-pull converter provided in anembodiment of the present application;

FIG. 10 is a schematic diagram of a magnetic integration double-endedconverter provided in an embodiment of the present application whensecondary windings each have one turn;

FIG. 11 is a schematic diagram of another magnetic integrationdouble-ended converter provided in an embodiment of the presentapplication when secondary windings each have one turn; and

FIG. 12 shows a magnetic integration half-bridge converter provided inEmbodiment 4 of the present application.

DETAILED DESCRIPTION OF THE EMBODIMENTS

In order to make the objectives, technical solutions, and advantages ofthe present application more comprehensible, the technical solutionsprovided in the present application are described in further detailbelow with reference to embodiments and the accompanying drawings.

An embodiment of the present application provides a magnetic integrationdouble-ended converter, which includes:

-   -   an inverter circuit with double ends symmetrically working,        acting on a primary winding;    -   an integrated magnetic member having a magnetic core with three        magnetic columns, including at least three windings and at least        one energy storage air gap, where the primary winding and a        first secondary winding are wound around a first magnetic        column, a second secondary winding is wound around a second        magnetic column, and a total output current flows through the        second secondary winding; and    -   a group of synchronous rectifiers, gate electrode driving        signals of which and gate electrode driving signals of a group        of power switch diodes of the inverter circuit with the double        ends symmetrically working complement each other.

The inverter circuit with the double ends symmetrically working may beany one of a half-bridge inverter circuit, a full-bridge invertercircuit, and a push-pull circuit. When the inverter circuit with thedouble ends symmetrically working is the half-bridge inverter circuit,the magnetic integration double-ended converter provided in theembodiment of the present application may also be called a magneticintegration half-bridge inverter; similarly, when the inverter circuitwith the double ends symmetrically working is the full-bridge invertercircuit or the push-pull circuit, the magnetic integration double-endedconverter provided in the embodiment of the present application may alsobe called a magnetic integration full-bridge inverter or magneticintegration push-pull inverter accordingly.

In an example that the inverter circuit with the double endssymmetrically working is the half-bridge inverter circuit, the magneticintegration double-ended converter provided in the embodiment of thepresent application may have the following specific structure.

Embodiment 1

FIG. 2 shows a magnetic integration half-bridge converter in Embodiment1, where a half-bridge inverter circuit on a primary side includesvoltage dividing capacitors C₁ and C₂ and power switch diodes S₁ and S₂.An integrated magnetic member of the magnetic integration half-bridgeconverter includes an EE-type magnetic core. The EE-type magnetic coreincludes three windings and two energy storage air gaps. A primarywinding N_(p) and a first secondary winding N_(s1) are wound around afirst magnetic column 1, a second secondary winding N_(s2) is woundaround a second magnetic column 2, an energy storage air gap 1 isdisposed on the second magnetic column 2, and an energy storage air gap2 is disposed on a third magnetic column 3. Two ends of the primarywinding N_(p) are respectively connected to a connection point A ofbridge arms of the power switch diodes S1 and S2 of the half-bridgeinverter circuit and a connection point B of the voltage dividingcapacitors C₁ and C₂ of the half-bridge inverter circuit.

The first secondary winding N_(s1), the second secondary winding N_(s2),an output filtering capacitor C_(o), and a first synchronous rectifierSR₁ form a power circuit on a secondary side; the second secondarywinding N_(s2), the output filtering capacitor C_(o), and a secondsynchronous rectifier SR₂ form another power circuit on the secondaryside. A series branch of the first synchronous rectifier SR₁ and thefirst secondary winding N_(s1) is connected to the second synchronousrectifier SR₂ in parallel. A current flowing through the secondsecondary winding N_(s2) is a sum of currents of the synchronousrectifiers SR₁ and SR₂.

Referring to FIG. 3 and FIG. 4, according to a working principle of asymmetrical half-bridge, the power switch diodes S1 and S₂ on theprimary side undergo driving voltages V_(g1) and V_(g2) having a phasedifference of 180° to form a square wave inverting voltage V_(AB) at thetwo ends of the primary winding N_(p). Driving voltages of thesynchronous rectifiers SR₁ and SR₂ on the secondary side arerespectively V_(gs1) and V_(gs2), where V_(gs1) and V_(g2) complementeach other, and V_(gs2) and V_(g1) complement each other. Therefore, aworking process of the circuit may be divided into four stages.

Stage 1 [t₀-t₁]: The power switch diode S1 on the primary side is turnedon and S₂ is turned off, and the synchronous rectifier SR₁ on thesecondary side is turned on and SR₂ is turned off. A voltage applied onthe two ends of the primary winding N_(p) is V_(in)/2, Φ₁ of the firstmagnetic column 1 where the primary winding is located is increasedlinearly, and magnetic fluxes Φ₂ and Φ₃ of other two magnetic columnsare increased accordingly. A current i_(SR1) of the first secondarywinding N_(s1) is equal to a current i_(out) of the second secondarywinding N_(s2).

Stage 2 [t₁-t₂]: The power switch diodes S1 and S₂ on the primary sideare both turned off, and the synchronous rectifiers SR₁ and SR₂ on thesecondary side are both turned on. A current i_(p) of the primarywinding is zero. The first secondary winding N_(s1) is shorted by SR₁and SR₂, so that voltages of the windings N_(p) and N_(s1) wound aroundthe first magnetic column 1 are zero, the magnetic flux Φ₁ remainsunchanged, and a decrease in the magnetic flux of the second magneticcolumn 2 is equal to an increment in the magnetic flux of the thirdmagnetic column 3. The two synchronous rectifiers on the secondary sideare both turned on, a part of the current i_(SR1) flowing through SR₁ istransferred to SR₂, and a sum of the currents of the two synchronousrectifiers on the secondary side is equal to i_(out).

Stage 3 [t₂-t₃]: The power switch diode S₂ on the primary side is turnedon and S₁ is turned off, and the synchronous rectifier SR₂ on thesecondary side is turned on and SR₁ is turned off. The voltage appliedon the two ends of the primary winding N_(p) is −V_(in)/2, Φ₁ of thefirst magnetic column 1 where the primary winding is located isdecreased linearly, and the magnetic fluxes Φ₂ and Φ₃ of other twomagnetic columns are decreased accordingly. The current i_(out) of thesecond secondary winding N_(s2) totally flows through the synchronousrectifier SR₂.

Stage 4 [t₃-t₄]: The power switch diodes S1 and S₂ on the primary sideare both turned off, and the synchronous rectifiers SR₁ and SR₂ on thesecondary side are both turned on. The current i_(p) of the primarywinding is zero. The first secondary winding N_(s1) is shorted by SR₁and SR₂, so that the voltages of the windings N_(p) and N_(s1) woundaround the first magnetic column 1 are zero, the magnetic flux Φ₁remains unchanged, and a decrease in the magnetic flux of the secondmagnetic column 2 is equal to an increment in the magnetic flux of thethird magnetic column 3. The two synchronous rectifiers on the secondaryside are both turned on, a part of the current i_(SR2) flowing throughSR₂ is transferred to SR₁, and a sum of the currents is equal toi_(out).

According to continuity of a magnetic flux, an input-to-output voltageconversion ratio may be derived:

${\frac{V_{o}}{V_{in}} = {\frac{N_{s\; 1}}{N_{p}}\frac{D}{2}}},$

where D refers to a duty cycle, which is obtained by dividing a turn-ontime of the power switch diode S_(i) by a switching period.

Embodiment 2

FIG. 5 shows a magnetic integration half-bridge converter of Embodiment2. The difference between the magnetic integration half-bridge converterof Embodiment 2 and the magnetic integration half-bridge converter ofEmbodiment 1 is that, an EE-type magnetic core of Embodiment 2 includesthree windings and one energy storage air gap. A primary winding N_(p)and a first secondary winding N_(s1) are wound around a first magneticcolumn 1, a second secondary winding N_(s2) is wound around a secondmagnetic column 2, an energy storage air gap 1 is disposed on a thirdmagnetic column 3, and the number of turns of the first secondarywinding N_(s1) is twice the number of turns of the second secondarywinding N_(s2).

Referring to FIG. 5, a working process of the circuit of Embodiment 2may also be divided into four stages:

Stage 1 [t₀-t₁]: The power switch diode S1 on the primary side is turnedon and S₂ is turned off, and the synchronous rectifier SR₁ on thesecondary side is turned on and SR₂ is turned off. A voltage applied onthe two ends of the primary winding N_(p) is V_(in)/2, Φ₁ of the firstmagnetic column 1 where the primary winding is located is increasedlinearly, a magnetic flux Φ₂ of the second magnetic column 2 isincreased linearly, and a magnetic flux Φ₃ of the third magnetic column3 is decreased linearly. A current i_(SR1) of the first secondarywinding N_(s1) is equal to a current i_(out) of the second secondarywinding N_(s2).

Stage 2 [t₁-t₂]: The power switch diodes S1 and S₂ on the primary sideare both turned off, and the synchronous rectifiers SR₁ and SR₂ on thesecondary side are both turned on. The current i_(p) of the primarywinding is zero. The first secondary winding N_(s1) is shorted by SR₁and SR₂, so that the voltages of the windings N_(p) and N_(s1) woundaround the first magnetic column 1 are zero, the magnetic flux Φ₁remains unchanged, and a decrease in the magnetic flux of the secondmagnetic column 2 is equal to an increment in the magnetic flux of thethird magnetic column 3. The two synchronous rectifiers on the secondaryside are both turned on, the current i_(SR1) flowing through SR₁ isequal to a current i_(SR2) flowing through SR₂, and a sum of the twocurrents is equal to i_(out).

Stage 3 [t₂-t₃]: The power switch diode S₂ on the primary side is turnedon and S₁ is turned off, and the synchronous rectifier SR₂ on thesecondary side is turned on and SR₁ is turned off. The voltage appliedon the two ends of the primary winding N_(p) is −V_(in)/2, Φ₁ of thefirst magnetic column 1 where the primary winding is located isdecreased linearly, and the magnetic fluxes Φ₂ and Φ₃ of other twomagnetic columns are decreased linearly. The current i_(out) of thesecond secondary winding Ns2 totally flows through the synchronousrectifier SR2.

Stage 4 [t₃-t₄]: The power switch diodes S1 and S2 on the primary sideare both turned off, and the synchronous rectifiers SR₁ and SR₂ on thesecondary side are both turned on. The current i_(p) of the primarywinding is zero. The first secondary winding N_(s1) is shorted by SR₁and SR₂, so that the voltages of the windings N_(p) and N_(s1) woundaround the first magnetic column 1 are zero, the magnetic flux Φ₁remains unchanged, and a decrease in the magnetic flux of the secondmagnetic column 2 is equal to an increment in the magnetic flux of thethird magnetic column 3. The two synchronous rectifiers on the secondaryside are both turned on, the current i_(SR1) flowing through SR₁ isequal to a current i_(SR2) flowing through SR₂, and a sum of the twocurrents is equal to i_(out).

According to continuity of a magnetic flux, an input-to-output voltageconversion ratio may be derived:

${\frac{V_{o}}{V_{in}} = {\frac{N_{s\; 1}}{N_{p}}\frac{D}{2}}},$

where D refers to a duty cycle, which is obtained by dividing a turn-ontime of the power switch diode S₁ by a switching period.

No energy storage air gap is disposed on the first magnetic column 1 andthe second magnetic column 2, so it can be considered that equivalentmagnetic resistance of the magnetic columns is zero. Therefore, anequivalent output filtering inductance L_(out) of Embodiment 2 may berepresented as:

${L_{out} = \frac{N_{s\; 2}^{2}}{R_{m\; 3}}},$

where R_(m) ₃ is equivalent magnetic resistance of the third magneticcolumn 3.

Embodiment 3

FIG. 7 shows a magnetic integration half-bridge converter of Embodiment3. On the basis of Embodiment 2, a third secondary winding N_(s3) isadded on a third magnetic column 3. Specifically, an EE-type magneticcore of Embodiment 3 includes four windings and one energy storage airgap. A primary winding N_(p) and a first secondary winding N_(s1) arewound around a first magnetic column 1, a second secondary windingN_(s2) is wound around a second magnetic column 2, the third windingN_(s3) is wound around the third magnetic column 3, an energy storageair gap 1 is defined in the third magnetic column 3, and the number ofturns of the first secondary winding N_(s1) is twice the number of turnsof the second secondary winding N_(s2).

In this case, the first secondary winding N_(s1), the second secondarywinding N_(s2), the third secondary winding N_(s3), an output filteringcapacitor C_(o), and a first synchronous rectifier SR₁ form a powercircuit on the secondary side; the second secondary winding N_(s2), thethird secondary winding N_(s3), the output filtering capacitor C_(o),and a second synchronous rectifier SR₂ form another power circuit on thesecondary side. A series branch of the first synchronous rectifier SR₁and the first secondary winding N_(s1) is connected to the secondsynchronous rectifier SR₂ in parallel. The second secondary windingN_(s2) and the third secondary winding N_(s3) are connected in parallel,so as to increase an output filtering inductance. A current flowingthrough the second secondary winding N_(s2) and the third secondarywinding N_(s3) is a sum of currents of the synchronous rectifiers SR₁and SR₂.

In comparison with Embodiment 2, in Embodiment 3, the third secondarywinding N_(s3) is added on the third magnetic column 3, so as to improvethe output filtering inductance of the circuit without influence on theworking mode of the circuit. Therefore, for working timing of thecircuit of the synchronous rectifier and the output circuit, referencemay also be referred to FIG. 6. In this case, an equivalent outputfiltering inductance L_(out) of Embodiment 3 may be represented as:

${L_{out} = \frac{\left( {N_{s\; 2} + N_{s\; 3}} \right)^{2}}{R_{m\; 3}}},$

where R_(m) ₃ is equivalent magnetic resistance of the third magneticcolumn 3.

Embodiment 4

FIG. 12 shows a magnetic integration half-bridge converter of Embodiment4. The difference between the magnetic integration half-bridge converterof Embodiment 4 and the magnetic integration half-bridge converter ofEmbodiment 1 is that, an EE-type magnetic core of Embodiment 4 includesthree windings and one energy storage air gap. A primary winding N_(p)and a first secondary winding N_(s1) are wound around a first magneticcolumn 1, a second secondary winding N_(s2) is wound around a thirdmagnetic column 3, an energy storage air gap 1 is disposed on the thirdmagnetic column 3, the number of turns of the first secondary windingN_(s1) is twice the number of turns of the second secondary windingN_(s2), and the first secondary winding N_(s1) is drawn out of thesecond secondary winding N_(s2).

A working process of the circuit of Embodiment 4 is the same as that ofEmbodiment 2.

In sum, in the example that the inverter circuit with the double endssymmetrically working is the half-bridge inverter circuit, in themagnetic integration double-ended converter provided in the embodimentof the present application, the primary winding and the first secondarywinding are wound around the same magnetic column, and a synchronousrectifier replaces a rectifier diode in the prior art, thereby reducinga turn-on loss of a switch device, and clamping the voltage of the firstsecondary winding N_(s1) to 0 in stages 2 and 4, so as to play a part inzero voltage drop clamping of the secondary winding. In this way, leastprimary windings may be adopted to implement energy transferring fromthe primary side to the secondary side, thereby reducing a loss of thewindings and a leakage inductance of the primary side and the secondaryside, and implementing high efficient conversion of energy.

It can be understood that, according to different topology structures ofinverter circuits, the inverter circuit with the double endssymmetrically working may also be the full-bridge inverter circuit andthe push-pull circuit, for example, a magnetic integration full-bridgeinverter in FIG. 8 and a magnetic integration push-pull converter inFIG. 9.

In the magnetic integration full-bridge inverter in FIG. 8, except thata topology structure of the inverter circuit on the primary side isdifferent from that of the magnetic integration half-bridge converter inFIG. 2, FIG. 5, or FIG. 7, windings on the primary side and thesecondary side are the same as those of the magnetic integrationhalf-bridge converter in FIG. 2, FIG. 5, or FIG. 7. The magneticintegration push-pull converter in FIG. 9 has two primary windings,being respectively N_(p1) and N_(p2), that is, has one more primarywinding than the full-bridge and the half-bridge, but the primarywindings N_(p1) and N_(p2) are wound around the same magnetic column,the winding structure on the secondary side is the same as that of themagnetic integration half-bridge inverter. Therefore, the working timingand internal magnetic fluxes Φ₁, Φ₂, and Φ₃ of forming magnetic cores ofthe magnetic integration full-bridge inverter in FIG. 8 and the magneticintegration push-pull converter in FIG. 9 are respectively the same asthose of the magnetic integration half-bridge converter of the presentapplication.

When the primary winding N_(p) and the first secondary winding N_(s1)are wound around the first magnetic column 1, and the second secondarywinding N_(s2) is wound around the second magnetic column 2, referringto FIG. 10, if the secondary windings N_(s1) and N_(s2) each have oneturn, a shadow region in FIG. 10 represents a copper sheet of asecondary winding power loop of an E shape with an upward opening andincluding three parts, where two parts of the copper sheet pass througha magnetic core window and are respectively windings N_(s1) and N_(s2),the third part is connected to the secondary rectifier SR₂ outside themagnetic core and is a trace part. The primary winding N_(p) is woundaround the first magnetic column 1. A part of the primary winding N_(p)is in the same winding window as N_(s1); and a part of the primarywinding N_(p) is exposed outside the magnetic core window, so as toensure a good coupling relationship between the part of the primarywinding N_(p) and the trace. In this way, the high efficient energyswitching from the primary winding N_(p) to the secondary windingsN_(s1) and N_(s2) can be implemented, and an effective zero voltage dropclamping function of SR₁ and SR₂ on the secondary windings can beensured.

The energy storage air gap of the E-shaped magnetic core is disposed onthe second magnetic column 2 and the third magnetic column 3 or isdisposed only on the third magnetic column 3, and therefore, in order tomore effectively control magnetic field distribution outside theintegrated magnetic member, in the magnetic integration double-endedconverter provided in the embodiment of the present application, theprimary winding N_(p) and the first secondary winding N_(s1) may also bewound around the second magnetic column 2 and the third magnetic column3 at the same time, and other structures keep the same.

Referring to FIG. 11, when the primary winding N_(p) and the firstsecondary winding N_(s1) are wound around the second magnetic column 2and the third magnetic column 3 at the same time, and the secondsecondary winding N_(s2) is wound around the second magnetic column 2,if the secondary windings N_(s1) and N_(s2) each have one turn, a shadowregion in FIG. 11 represents a copper sheet of a secondary winding powerloop of an E shape with an upward opening and including three parts,where two parts of the copper sheet pass through a magnetic core windowand are respectively windings N_(s1) and N_(s2), the third part isconnected to the secondary rectifier SR₂ outside the magnetic core andis a trace part. The primary winding N_(p) is wound around the secondmagnetic column 2 and the third magnetic column 3. A part of the primarywinding N_(p) is in the same winding window as N_(s1); and a part of theprimary winding N_(p) is exposed outside the magnetic core window, so asto ensure a good coupling relationship between the part of the primarywinding N_(p) and the trace. The difference between FIG. 11 and FIG. 10is that, the trace part follows the external side of the primary windingN_(p) being wound around the second magnetic column 2, so as to ensurekeeping good coupling with the primary part.

Based on the foregoing description, an embodiment of the presentapplication provides another magnetic integration double-endedconverter, which includes:

-   -   an inverter circuit with double ends symmetrically working,        acting on a primary winding;    -   an integrated magnetic member having a magnetic core with three        magnetic columns, including at least three windings and at least        one energy storage air gap, where the primary winding and a        first secondary winding are both wound around a second magnetic        column and a third magnetic column, a second secondary winding        is wound around the second magnetic column, and a total output        current flows through the second secondary winding; and    -   a group of synchronous rectifiers, gate electrode driving        signals of which and gate electrode driving signals of a group        of power switch diodes of the inverter circuit with the double        ends symmetrically working complement each other.

In an embodiment, the integrated magnetic member having the magneticcore with the three magnetic columns includes three windings and twoenergy storage air gaps, where the primary winding and the firstsecondary winding are both wound around the second magnetic column andthe third magnetic column, the second secondary winding is wound aroundthe second magnetic column, the total output current flows through thesecond secondary winding, and the energy storage air gaps arerespectively disposed on the second magnetic column and the thirdmagnetic column. In this embodiment, the number of turns of the firstsecondary winding and the number of turns of the second secondarywinding are not limited and may be the same or different.

In another embodiment, the integrated magnetic member having themagnetic core with the three magnetic columns includes three windingsand one energy storage air gap, where the primary winding and the firstsecondary winding are both wound around the second magnetic column andthe third magnetic column, the second secondary winding is wound aroundthe second magnetic column, the total output current flows through thesecond secondary winding, and the energy storage air gap is disposedonly on the third magnetic column. In this embodiment, the number ofturns of the first secondary winding is required to be twice the numberof turns of the second secondary winding.

In yet another embodiment, the integrated magnetic member having themagnetic core with the three magnetic columns includes four windings andone energy storage air gap, where the primary winding and the firstsecondary winding are both wound around the second magnetic column andthe third magnetic column, the second secondary winding is wound aroundthe second magnetic column, the third secondary winding is wound aroundthe third magnetic column, the third secondary winding is connected tothe second secondary winding in series, the total output current flowsthrough the third secondary winding and the second secondary winding,and the energy storage air gap is disposed only on the third magneticcolumn. In this embodiment, the number of turns of the first secondarywinding is also required to be twice the number of turns of the secondsecondary winding.

It can also be understood that, the inverter circuit with the doubleends symmetrically working included in the magnetic integrationdouble-ended converter may be any one of the half-bridge invertercircuit, the full-bridge inverter circuit, and the push-pull circuit,and can generate a square wave voltage signal acting on the primarywinding.

It should be noted that, whether the primary winding and the firstsecondary winding are both wound around the first magnetic columnwithout the energy storage air gap or are both wound around the secondmagnetic column and the third magnetic column with at least one energystorage air gap disposed, when the first secondary winding and/or thesecond secondary winding has one turn, the length of the winding isreduced, so the actual requirement is satisfied, and meanwhile, the lossof the winding can be reduced.

It should be finally noted that, the magnetic integration double-endedconverter provided in the embodiment of the present application may beapplicable to a direct current-direct current (DC-DC) secondary powersource module as a communication device.

The foregoing embodiments are not intended to limit the presentapplication. For persons skilled in the art, any modification,equivalent replacement, and improvement made without departing from theprinciple of the present application shall fall within the protectionscope of the present application.

1. A magnetic integration double-ended converter, comprising: aninverter circuit with double ends symmetrically working, acting on aprimary winding; an integrated magnetic member having a magnetic corewith three magnetic columns, comprising at least three windings and atleast one energy storage air gap, wherein the primary winding and afirst secondary winding are both wound around a first magnetic column, asecond secondary winding is wound around a second magnetic column, and atotal output current flows through the second secondary winding; and agroup of synchronous rectifiers, gate electrode driving signals of whichand gate electrode driving signals of a group of power switch diodes ofthe inverter circuit with the double ends symmetrically workingcomplement each other.
 2. The magnetic integration double-endedconverter according to claim 1, wherein the second magnetic column and athird magnetic column each define the at least one energy storage airgap therein.
 3. The magnetic integration double-ended converteraccording to claim 2, wherein the first secondary winding and/or thesecond secondary winding has one turn.
 4. The magnetic integrationdouble-ended converter according to claim 1, wherein the energy storageair gap is disposed only on a third magnetic column, and the number ofturns of the first secondary winding is twice the number of turns of thesecond secondary winding.
 5. The magnetic integration double-endedconverter according to claim 4, wherein a third secondary winding isadded on the third magnetic column, the third secondary winding isconnected to the second secondary winding in series, and the totaloutput current flows through the third secondary winding and the secondsecondary winding.
 6. The magnetic integration double-ended converteraccording to claim 1, wherein the energy storage air gap is disposedonly on the second magnetic column, and the number of turns of the firstsecondary winding is twice the number of turns of the second secondarywinding.
 7. The magnetic integration double-ended converter according toclaim 6, wherein a third secondary winding is added on the secondmagnetic column, the third secondary winding is connected to the secondsecondary winding in series, and the total output current flows throughthe third secondary winding and the second secondary winding.
 8. Themagnetic integration double-ended converter according to claim 1,wherein the inverter circuit with the double ends symmetrically workingis any one of a half-bridge inverter circuit, a full-bridge invertercircuit, and a push-pull circuit.
 9. A magnetic integration double-endedconverter, comprising: an inverter circuit with double endssymmetrically working, acting on a primary winding; an integratedmagnetic member having a magnetic core with three magnetic columns,comprising at least three windings and at least one energy storage airgap, wherein the primary winding and a first secondary winding are bothwound around a second magnetic column and a third magnetic column, asecond secondary winding is wound around the second magnetic column, anda total output current flows through the second secondary winding; and agroup of synchronous rectifiers, gate electrode driving signals of whichand gate electrode driving signals of a group of power switch diodes ofthe inverter circuit with the double ends symmetrically workingcomplement each other.
 10. The magnetic integration double-endedconverter according to claim 9, wherein the second magnetic column andthe third magnetic column each define the at least one energy storageair gap therein.
 11. The magnetic integration double-ended converteraccording to claim 10, wherein the first secondary winding and/or thesecond secondary winding has one turn.
 12. The magnetic integrationdouble-ended converter according to claim 9, wherein the energy storageair gap is disposed only on the third magnetic column, and the number ofturns of the first secondary winding is twice the number of turns of thesecond secondary winding.
 13. The magnetic integration double-endedconverter according to claim 12, wherein a third secondary winding isadded on the third magnetic column, the third secondary winding isconnected to the second secondary winding in series, and the totaloutput current flows through the third secondary winding and the secondsecondary winding.
 14. The magnetic integration double-ended converteraccording to claim 9, wherein the inverter circuit with the double endssymmetrically working is any one of a half-bridge inverter circuit, afull-bridge inverter circuit, and a push-pull circuit.